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IRS29831pbf 1 www.irf.com ? 20 14 international rectifier september 10 , 2014 le d flyback control ic features ? flyback led driver ? integrated 700 v mosfet ? critical - conduction / transition mode operation ? primary constant power control ? burst mode operation at light load ? over - current protection ? micro power startup (150 a) ? low quiescent current (2.5 ma) ? latch immunity and esd protection ? open load / o ver voltage protection ? compatible with triac dimmers ? high power factor / low thd typical applications ? led drivers product summary topology flyback drain source voltage 700 v max drain current 0.65 a max converter power 25 w p ackage 8- lead dip ordering information base part number package type standar d pack complete part number form quantity irs2983 1 pbf dip 8 tube/bulk 50 irs2983 1 pbf
IRS29831pbf 2 www.irf.com ? 20 14 international rectifier september 1 0 , 2014 table of contents page ordering information 1 description 3 absolute maximum ratings 4 recommended operating conditions 4 electrical characteristics 5 funct ional block diagram 7 state diagram 8 input/output pin equivalent circuit diagram 9 lead definitions 10 lead assignments 10 application information and additional details 11 package details 1 5 part marking information 1 6 qualification information 1 7
IRS29831pbf 3 www.irf.com ? 20 14 international rectifier september 1 0 , 2014 description the irs2983 1 is a n integrated led driver control ic and power mosfet designed to drive flyback and buck - boost converter based led drivers. the irs2983 1 include s primary side power regulation allow ing a low cost isolated or non - isolated led driver to be implemente d without the need for an opto - isolator for a fixed led load . the irs2983 1 is also compatible with converters that include secondary feedback circuitry . other features of the irs2983 1 include a high voltage startup enabling vcc supp ly to be derived initially from the high voltage dc bus until the auxiliary flyback inductor winding take s over for rapid startup . the irs2983 1 typically operates in critical conduction (crcm) with full protect ion against open and short circuit as well as inductor saturation. the irs2983 1 may be used in singl e stage led drivers with no dc bus smoothing capacitor enabl ing high power factor and low thd with minimal component count . typical connection diagram (non - dimming) dfb t 1 br 1 cin cvout rcs dvcc ic 1 rin rdc rzx 1 ac line input cdc ccomp drn vcc hv vdc cs zx comp com irs 29831 7 6 5 1 2 3 4 8 rzx 2 cvcc rout csnub rsnub dsnub dzvcc rvcc
IRS29831pbf 4 www.irf.com ? 20 14 international rectifier september 1 0 , 2014 a bs olute maximum ratings absolute maximum ratings indicate sustained limits beyond which damage to the device may occur. all voltage parameters are absolute voltages referenced to com; all currents are defined positive into any lead. the thermal resistance an d power dissipation ratings are measured under board mounted and still air conditions. symbol definition min. max. units v ds drain - source voltage --- 700.0 v i ds drain current at 25oc ? --- 0.65 a i ds drain current at 100oc ? --- 0.4 v cc ic low voltage supply ?? - 0.3 20.8 v i cc vcc current 0 25 .0 ma v hv hv pin voltage - 0.3 600 v i hv hv pin current 0 5.0 ma v ds drain pin voltage - 0.3 700 v v comp comp pin voltage - 0.3 v cc +0.3 v v dc vdc pin voltage v zx zx pin voltage v cs vcs pin voltage i c omp comp pin current - 5 5 ma i dc v dc pin current i zx zx pin current i cs cs pin current p d package power dissipation @ t a +25oc p d = (t jmax - t a )/r ja (8 - pin dip ) --- 1 w r ja thermal resistance, ju nction to ambient (8 - pin dip ) --- 125 oc/w t j junction temper ature - 55 1 25 oc t s storage temperature - 55 1 25 t l lead temperature (soldering, 10 seconds) --- 300 recommended operating conditions for proper operation the device should be used within recommended conditions. symbol definition min. max. units v c c supply voltage v ccuv+ 18 v i cc v cc supply current note 2 10 ma i cs cs pin current - 1 1 i dc v dc pin current i zx zx pin current i comp comp pin current v dc v dc pin voltage 0 6 .0 v v cs v cs pin voltage 0.1 2.0 t j junction temperature - 25 10 0 oc ? : the mosfet device used in this product is rated to 4a. it has been de - rated to conform to the thermal limits of the dip8 package assuming no heat sink is attached. ? ? : this ic contains a zener clamp structure between the chip vcc and com whic h has a nominal breakdown voltage of 20v. this supply pin should not be driven by a dc, low impedance power source greater than the vclamp specified in the electrical characteristics section.
IRS29831pbf 5 www.irf.com ? 20 14 international rectifier september 1 0 , 2014 electrical characteristics v cc = v bias =14v +/ - 0.25v, c out = 1 000pf, v comp = v oc = v dc = v zx = 0v, t a =25 o c unless otherwise specified symbol definition min typ max units test conditions mosfet characteristics v ds max maximum drain - source voltage 700.0 --- --- v i d max maximum continuous drain current --- --- 0.65 a source - drain diode characteristics v sd diode forward voltage --- --- 1.4 v t rr reverse recovery time --- 437.0 --- ns q rr reverse recovery charge --- 2.2 --- c supply characteristics v ccuv + v cc supply under v oltage positive going threshold 11.5 12.5 13.5 v v ccuv - v cc supply under v oltage negative going threshold 9.5 10.5 11.5 v uvhys v cc supply under v oltage lockout hysteresis 1.5 2.0 3.0 i qccuv uvlo mode v cc quiescent current --- 150 --- a v cc = 6v i cc v cc supply current --- 2.5 5.0 ma v clamp v cc zener clamp voltage 19.8 20.8 21.8 v i cc = 10ma high voltage startup characteristics v hvsmin minimum startup v oltage 3 0.0 --- --- v i hv_charge v cc c harge c urrent 1 2 --- ma v cc < v ccuv - hv=100v~400v i hvs_off high v oltage start - up circuit off state leakage c urrent --- --- 50 a hv=400v error amplifier characteristics i compsource comp pin error amplifier output current sourcing --- 30 --- a i compsink comp pin error amplifier output current sinking --- 30 --- v compoh error amplifier output voltage swing (high state) --- 13.5 --- v v compol error amplifier output voltage swing (low state) --- 2.5 --- gbd v compflt error amplifier output voltag e in fault mode --- 0 --- i v dc input bias current --- - 1 -- a v dc =0 to 3v control characteristics v zx+ zx pin threshold voltage (arm) 1.40 1.54 1.68 v v zx - zx pin threshold voltage (trigger) 0.52 0.6 0.68 v pref power regulation reference --- 1.00 --- k mult multiplier gain 1.90 2.00 2.10 v cs =0.5v t blan k oc pin current - sensing blank time 160 200 264 ns v dc =2.5v comp=4.0v cs=1.5v
IRS29831pbf 6 www.irf.com ? 20 14 international rectifier september 1 0 , 2014 electrical characteristics (cont?d) v cc = v bias =14v +/ - 0.25v, c out = 1000pf, v comp = v oc = v dc = v zx = 0v, t a =25 o c unless otherwise specified. t wd pfc watch - dog pulse interv al 65 100 135 s zx = 0 comp = 4.0v t onmin pwm minimum on time 2 20 28 0 34 0 ns ?? t onmax pwm maximum on time 22 32 42 s zx = 0 comp = 13v ?? t offmin pwm minimum off time 2.7 3.0 3.3 ?? v dcmax maximum voltage for multiplier input ? --- --- 7.0 v gbd v cspkmax maximum peak voltage for multiplier input ? --- --- 1.0 v signal is averaged before entering multiplier input. gbd protection circuitry characteristics v csth cs pin over - current sense threshold 1.19 1.25 1.31 v v compoff cut off voltage below which gate drive o utput is disabled 1.12 1.40 1.68 v compoff_hys cut off voltage hysteresis --- 40 --- mv v ovth zx pin over - voltage comparator threshold 4.90 5. 15 5. 40 v v ovhys zx pin over - voltage comparator hysteresis --- 200 --- mv ? : multiplier operates accu rately from zero to the maximum input specified. ??: measured at the drain with mosfet switching delay also included. gbd : guaranteed by design.
IRS29831pbf 7 www.irf.com ? 20 14 international rectifier september 1 0 , 2014 functional block diagram drn comp zx vzx vcc 5 1 2 vovth vclamp vdc 8 hv startup hv 7 vpref vcc 6 com 4 uvlo q s r q watchdog timer vcsth q s r q set dominant blank time averager cs 3 x k mult
IRS29831pbf 8 www.irf.com ? 20 14 international rectifier september 1 0 , 2014 state diagram uvlo mode icc = iqccuv hvreg = on out = low comp = held low power turned on startup mode out = switching vcc > vccuv+ fault mode out = low comp = held low vzx > vovth current limit out = low vcs > vcsth vzx < vovth- vovhys delay twd regulating mode hvreg = off out = switching vmult > vpref vcs < vcsth -vovhys vcs > vcsth vcs < vcsth -vovhys vzx > vovth
IRS29831pbf 9 www.irf.com ? 20 14 international rectifier september 1 0 , 2014 input/output pin equivalent circuit diagrams vcc com comp , vdc , cs , zx esd diode esd diode vclamp
IRS29831pbf 10 www.irf.com ? 20 14 international rectifier september 1 0 , 2014 lead definitions symbol description comp compensation and averaging capacitor input zx pfc zero - crossing & over - voltage detection cs pfc current sensing input com ic power & signal ground drn mosfet drain vcc logic & low - side gate driver supply hv high voltage startup input vdc dc bus voltage input lead assignments drn vcc hv vdc cs zx comp com IRS29831 7 6 5 1 2 3 4 8
IRS29831pbf 11 www.irf.com ? 20 14 international rectifier september 1 0 , 2014 application information and additional details the irs2983 1 is a switched mode controller ic with an in tegrated high voltage mosfet de s i gned for use in flyback and buck - boost converters . an internal high voltage regulator is included to supply the ic l ow voltage vcc supply allowing operation directly from a dc input voltage up to 600v with rapid startup at low and high ac line inputs . internal high voltage startup in order to begin operating , the irs2983 1 requires its vcc supply to be raised above the under voltage lockout positive threshold (vccuv+) and t o continue ope r ating requires vcc to be maintained above the under voltage lockout negative threshold (vccuv - ). the internal high voltage start up circuit provides the initial vcc voltage until an au xiliary windin g from the converter transformer take s over. a series resistor rvcc and 18v zener clamp dzvcc or other voltage limiting scheme is necessary in line with vcc to prevent damage to the IRS29831 if the auxiliary winding voltage exceeds the intern al clamp voltage (vclamp) . the hv regulator enables the irs2983 1 based led driver to start up very rapidly and deliver light within 0.5s of switch on at any line input voltage . when the converter reaches steady state and vcc can be supplied through the au xiliary winding the hv regulator switches off for zero power dissipation. the irs2983 1 is primarily targeted at led driver applications up to 25 w using isolated or non - isolated flyback converter or buck - boost topologies . the auxiliary winding is also use d to detect output voltage a nd zero - crossing point . in the event of a short circuit at the output , the vcc supply from the auxiliary winding collapses causing the IRS29831 to enter under voltage lockout and shut down . t he startup sequence is then re - initi alized continuing in ? hiccup ? mode until the short circuit is removed . short circuit prot ection is therefore auto - recovering enabling the driver to tolerate the condition without damage to the components. a capacitor in the order of 10pf at the zx may be r equired for correct operation. primary power regulation t o eliminate feedback circuitry and opto - isolators where the load consists of a fixed number of leds , the irs2983 1 is capable of regulating the output current indirectly by calculating and controll ing the input power of the converter. since an led load has an approximately fixed voltag e the power consumed is proportional to the current. in practice there are variations in led forward voltage drop due to tolerance and temperature, however perfect acc uracy is not usually required in such applica tions . for a fixed number of led s the current will be approximately proportional to the input power allowing output current regulation of +/ - 5% over line input from 120vac to 230vac. power regulation has been sh own to provide slightly less lumen output variation than current regulation. the irs2983 1 senses input voltage and current then averages and multiplies these quantities to determine the input power . this is then regulated against an accurate fixed referenc e to control the led current. the line i nput voltage is sensed through a resistor divider (rin and rdc) to provide a voltage within th e range from 0v to vdcmax. primary current is sensed through shunt resistor (rcs) connected from the source of the flyback mosfet switch to the dc b us return . this waveform is a high frequency ramp rising from zero at the beginning of each switching cycle to reach a peak level at the point the mosfet is switched off, remaining at zero during the off time. t ts v(t) vout(t) vcs(t) figure 1: current sense waveform a transconductance error amplifier (ota) uses an external capacitor (ccomp) referenced to 0v to realize an integrator t hat provide s a stable error voltage used to control the pwm on time. a response time of seve ral ac line cycles is normally used as in typical power f actor correction circuits to enable high power factor and low thd.
IRS29831pbf 12 www.irf.com ? 20 14 international rectifier september 1 0 , 2014 led output current typically increases gradually as the i nput voltage is increased. at light loads the irs2983 1 operates in burst mode to minimize losses and maintain a stable output when the comp output voltage drops below the vcompoff threshold. primary current limiting at low line input voltages the power regulation loop demands a high peak current which can cause saturation of the primary inductor. in order to prevent this from occurring , the irs2983 1 includes cycle by cycle primary current limiting with a fixed threshold vcsth at the cs pin input. under low line or fault conditions where the mosfet current is abnormally high , t he gate drive switches off as the current ramps up above vcsth with a leading edge blanking period of tblank. leading edge blanking avoid s false tripping due to the fast high current switch on transient caused by parasitic capacitances in the internal mosf et . this transient is also blanked from the averaging input that feeds the power regulation multiplier to prevent inaccuracies. the irs2983 1 normally operates in critical conduction mode (crcm), also known as transition or boundary mode. the flyback transf ormer auxiliary winding used to supply vcc is also used to provide the zero crossing or demagnetization signal to the irs2983 1 . this indicates when all of the energy stored in the inductor has been transferred to the output to trigger the next switching c ycle. the auxiliary winding voltage is divided through rzx1 and rzx2 to provide the zx pin input signal . t ts v(t) vout(t) vcs(t) vcsth figure 2: cycle by cycle current limiting the pulse appear ing at zx has an amplitude proportional to the secondary out put voltage and therefore the dc output voltage: ) 2 1 ( 2 rzx rzx n vout rzx n vzx s a + ? ? ? = [1] where , n a = number of turns on the auxiliary winding n s = number of turns on the secondary winding vout = dc output voltage (led voltage) when the IRS29831 inte grated mosfet switches off the voltage vzx transitions high . t he values of rzx1 and rzx2 must be selected so that this voltage always exceeds the vzx+ threshold. it should be noted that if the irs2983 1 is used in a converter that is required to drive loads with different numbers of leds with a range of voltage , an additional feedback circuit is needed to regulate the output current. in this case the vzx voltage needs to exceed vzx+ at the minimum load voltage. if vzx does not exceed vzx+ the irs2983 1 will o perate in discontinuous mode (dcm) with a fixed time of twd . when the voltage at vzx exceeds vzx+ the irs2983 1 is armed. it then waits until vzx dr ops below vzx - again to trigger the next switching cycle. the irs2983 1 includes a minimum off time function so that if the zx pin input transitions high and low before toffmin the gate drive output will not go high again until after this period. this prevents false tripping at the zx in put and also limits the maximum switching frequ ency of the converter by ente ring discontinuous mode (dcm) under conditions where the off time would otherwise be very short. this reduces switching losses and prevents transformer overheating. t ts v ( t) vout(t) vzx(t) figure 3: zero crossing detection
IRS29831pbf 13 www.irf.com ? 20 14 international rectifier september 1 0 , 2014 integrated mosfet the ir s29 831 includes an internal 700v rated mosfet with low rdson to enable dr iver operation up to 25 w with minimal temperature rise. a snubber network consisting of dsnub, csnub and rsnub is required in flyback converters to limit the peak ringing transient . i n a typical circuit with appropriate snubber values the transien t will not exceed 650v at maximum line input. over voltage protection the zx input is also used for output over voltage protection. i f the load becomes disconn e cted the output voltage c ould potentially rise very high damaging components as well as present ing an electric shock hazard. in order to protect against this the irs2983 1 is able to detect the output voltage indirectly through the proportional zx input . if the zx input voltage exceeds vovth when the mosfet switches off , the gate drive switche s off and remain s off for a period of twd before beginning the next cycle irrespective of when the zx voltage transitions low. in this case the irs2983 1 discharges the comp capacitor so that the ne xt cycle will begin at reduced duty cycle . w hen the open ci rcuit is removed the converter recovers with a soft start. this protection scheme allows the led load to be ? hot ? connected and disconnected from the converter output without risk of damaging the c ircuit or of high voltages appearing at the output. the overvoltage threshold is set by choosing the values of rzx1 and r zx2 appropriately, according to the formula: 2 ) 2 1 ( rzx n rzx rzx n vovth vout a s ov ? + ? ? = [2] the recommended over voltage threshold is 20- 25% above the normal operating voltage of the led load. this is important since re - connecting an led load with the output capacitor charged to a higher voltage causes a high current discharge that can cause severe damage to leds. a bleed resistor is also recommended to discharge the output capacitor. t twd v(t) vout(t) vzx(t) vcomp(t) figure 4: overvoltage protection operating with a secondary feedback circuit in applications where more accurate current regulation over a wide input and/or output voltage range required t he IRS29831 can be used in conjunction with a secondary sensing and feedback circuit. this technique is also applied in designs where dimming to low levels is required for example in a 0 - 10v controlled dimmable led driver. the feedback circuit can be fed t hrough a n opto - isolator or from the output of an operational amplifier if isolation is not required . t 1 rcs dvcc ic 1 rzx 1 drn vcc hv vdc cs zx comp com irs 29831 7 6 5 1 2 3 4 8 rzx 2 cvcc secondary error feedback rpu figure 5: secondary feedback circuit a simple output voltage feedback scheme is shown in figure 5 to demonstrate how the opto - isolator can be connected to the IRS29831 to create a feedback circuit. the vdc input is tied to com leaving the multiplier output at zero with the comp output pulled up to maximum by the internal error amplifier . the opto - isolator feedback
IRS29831pbf 14 www.irf.com ? 20 14 international rectifier september 1 0 , 2014 pulls down on the comp voltage to reduce the on time as the opto - diode current is increased driven by a secondary error amplifier circuit. a pull up resistor (rpu) may be added to improve stability. triac dimming a triac dimming led driver can be easily implemente d with the IRS29831 using a small number of additional components. the dimming design should be optimized to work in either the 120vac or 220vac range. it is not practical to create a design with good dimming performance and efficiency for both input volta ges. the dimming driver implementation consists of a single stage high power factor converter p reviously described with anti - ringing and active damping circuits added to the input to provide triac stability. the comp output is also clamped to a maximum le vel by adding an external zener diode dz3 referenced to com. this prevents the primary side regulation circuit from attempting to compensate for the reduced ac input voltage detected during dimming. du ring dimming the converter operate s with the on time de termined by the voltage at which comp is limited by the zener diode. a value of 6.8v typically provides good results for a 120vac system. the schematic below shows a full implementation of a 120vac triac dimmable led driver. rpd and cpd for the anti - ringin g network to suppress high frequency oscillations that typically occur when the dimmer triac fires caused by the interaction of the dimmer with the led driver input filter. typical values for rpd and cpd are 470ohms (1w) and 100nf to 220nf (250v). the acti ve damping circuit based around a low voltage mosfet md is used to limit the inrush current when the triac fires. at the start of each line cycle the triac is in the off state and during this time m d is turned off while q d holds the gate low. this means th at when the triac fires the series damping resistor rd limits the input current for a period of time until m d switches on. zener diode d z 2 normally rated at 10v prevents m d from switching on due to residual leakage voltages that appear on the dc bus during the period before the triac fires. after the triac fires a voltage appears at d z 1 which is typically rated at 16v. this causes q d to switch off and c d to charge through rp1, rp2 and dd. after the delay determined by these components , md switches on shorti ng out rd to remove the damping resistance when it is no longer necessary. typical values for rp1, rp2 are 680k and cd is 4.7nf. dd can be a typical small diode such as a 1n4148. the active circuit is designed to provide input resistance to damp the circui t at the firing point without incurring unnecessary power losses in the damping resistor rd. a typical value for rd is 100ohms rated at 2w. if some power loss can be tolerated in th e interests of saving component cost rd can be reduced in value and md and the components driving its gate can be removed. this low cost approach can still provide acceptable dimming performance with a small loss in converter efficiency. triac dimmable led driver dfb t 1 br 1 cin cvout rcs dvcc ic 1 rin rdc rzx 1 ac line input cdc ccomp drn vcc hv vdc cs zx comp com irs 29831 7 6 5 1 2 3 4 8 rzx 2 cvcc rout cpd rpd dz 1 dz 2 rd md cd dd qd rb rp 1 rp 2 csnub rsnub dsnub rvcc dzvcc dz 3
IRS29831pbf 15 www.irf.com ? 20 14 international rectifier september 1 0 , 2014 package details
IRS29831pbf 16 www.irf.com ? 20 14 international rectifier september 1 0 , 2014 part marking information IRS29831 ir logo yww ? part number date code pin 1 identifier lot code (prod mode ? 4 digit spn code) assembly site code per scop 200-002 ? xxxx marking code lead free released non-lead free released ? p
IRS29831pbf 17 www.irf.com ? 20 14 international rectifier september 1 0 , 2014 qualification information ? qualification level industrial ?? comments: this family of i c s has passed jedec?s industrial qualification. ir?s consumer qualification level is granted by extension of the higher i ndustrial level. esd machine model class b (per jedec standard jesd22 - a115) human body model class 1c (per ansi/esda /jedec standard js - 001 - 2012 ) ic latch - up test class i, level a (per jesd78) rohs compliant yes ? qualification standards can be found at international rectifier?s web site http://www.irf.com/ ?? higher qualification ratings may be available should the user have such requirements. please contact your international rectifier sales representative for f urther information. ??? higher msl ratings may be available for the specific package types listed here. please contact your international rectifier sales representative for further information. the information provided in thi s document is believed to be accurate and reliable. however, international rectifier assumes no responsibility for the consequences of the use of this information. international rectifier assumes no responsibility for an y infringement of patents or of oth er rights of third parties which may result from the use of this information. no license is granted by implication or otherwise under any patent or patent rights of international rectifier. the specifications mentioned in this document are subject to change without notice. this document supersedes and replaces all information previously supplied. for technical support, please contact ir?s technical assistance center http://www.irf.com/technical - info/ world headquarters: 233 kansas st., el segundo, california 90245 tel: (310) 252 - 7105

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