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rev. 0.4 june 2012 www.aosmd.com page 1 of 15 aoz1283 ezbuck? 2.5a simple buck regulator general description the aoz1283 is a high voltage, high efficiency, simple to use, 2.5a buck regulator optimized for a variety of applications. the aoz1283 works from a 3.0v to 36v input voltage range, and provides up to 2.5a of continuous output current. the output voltage is adjustable from 30v down to 0.8v. the aoz1283 integrates an n-channel high-side power mosfet. the switching frequency can set from 200khz to 2mhz with an external resistor. the soft-start time can be set with an external capacitor. features ? 3.0v to 36v operating input voltage range ? 50m ? internal nmos ? up to 95% efficiency ? adjustable soft-start ? output voltage adjustable from 0.8v to 30v ? 2.5a continuous output current ? adjustable switching frequency from 200khz to 2mhz ? cycle-by-cycle current limit ? short-circuit protection ? over-voltage protection ? over-temperature protection ? epad so-8 package applications ? point-of-load dc/dc conversion ? set top boxes and cable modems ? dvd drives and hdds ? lcd monitors & tvs ? telecom/networking/datacom equipment typical application figure 1. 36v/2.5a buck regulator comp vin en fsw lx bs gnd fb aoz1283 22h l1 cin rc cc css r1 r2 co vin up to 36v ss rf vout
aoz1283 rev. 0.4 june 2012 www.aosmd.com page 2 of 15 ordering information aos green products use reduced levels of halogens, and are also rohs compliant. please visit www.aosmd.com/media/aosgreenpolicy.pdf for additional information. pin configuration pin description part number ambient temperature range package environmental AOZ1283PI -40 c to +85 c epad so-8 green product pin number pin name pin function 1 lx pwm output. connect to inductor. 2 bst bootstrap voltage input. driver supply for high-side nmos. connected to 100nf capacitor between bst and lx. 3 gnd ground. 4 fsw frequency bias. connect to resistor to determine switching frequency. 5 comp compensation. connect to resistor and capacitor for system stability. 6 fb feedback input. it is regulated to 0.8v. th e fb pin is used to determine the pwm output voltage via a resistor divider between the output and gnd. 7 ss soft start. 8 en enable. exposed pad vin supply voltage input. lx 1 en 8 bst 2 ss 7 gnd 3 fb 6 fsw 4 comp 5 exposed pad vin
aoz1283 rev. 0.4 june 2012 www.aosmd.com page 3 of 15 absolute maximum ratings exceeding the absolute maxi mum ratings may damage the device. note: 1. devices are inherently esd s ensitive, handling precautions are required. human body model rating: 1.5k ? in series with 100pf. recommended operating conditions the device is not guaranteed to operate beyond the recommended operating conditions. electrical characteristics t a = 25 c, v in = 12v, v en = 3v, v out = 3.3v, unless otherwise sp ecified. specifications in bold indicate a temperature range of -40c to +85c. these specific ations are guaranteed by design. parameter rating supply voltage (v in ) 40v lx to gnd -0.7v to v in + 0.3v en, ss, fb and comp to gnd -0.3v to +6v bst to gnd -0.3v to v lx + 6v junction temperature (t j ) +150c storage temperature (t s ) -65c to +150c esd rating (1) 2kv parameter rating supply voltage (v in ) 3.0v to 36v output voltage (v out ) 0.8v to v in *0.85v ambient temperature (t a ) -40c to +85c package thermal resistance epad so-8 ( ? ja )50c/w symbol parameter conditions min. typ. max. units v in supply voltage 336 v v uvlo input under-voltage lockout threshold v in rising v in falling 2.3 2.9 v v i in supply current (quiescent) i out = 0, v fb = 1v, v en > 1.2v 11.5 ma i off shutdown supply current v en = 0v 10 ? a v fb feedback voltage t a = 25oc 788 800 812 mv v fb_load load regulation 0.4a < load < 3.6a 0.5 % v fb_line line regulation load = 2a 0.03 %/v i fb feedback voltage input current v fb = 800mv 0.8 ? a enable v en_off v en_on en input threshold off threshold on threshold 1.2 0.4 v v v en_hys en input hysteresis 200 mv current limit peak current limit 3 4 a soft start (ss) i ss soft start source current 2 2.5 3 ? a modulator f o frequency rf = 270k ? rf = 46.6k ? rf = 20k ? 160 0.8 1.6 200 1 2 240 1.2 2.4 khz mhz mhz d max maximum duty cycle f o = 1mhz 87 % t on_min minimum on time 150 ns gvea error amplifier voltage gain 500 v/v gea error amplifier transconductance 170 ? a/v gcs current sense circuit transconductance 4.5 a/v
aoz1283 rev. 0.4 june 2012 www.aosmd.com page 4 of 15 power state output i leakage nmos leakage v en = 0v, v lx = 0v 10 ? a r ds(on) nmos on-resistance v in = 12v 50 70 m ? thermal protection t sd thermal shutdown threshold 145 c t sd_hys thermal shutdown hysteresis 45 c symbol parameter conditions min. typ. max. units electrical characteristics ( continued ) t a = 25 c, v in = 12v, v en = 3v, v out = 3.3v, unless otherwise specified. specifications in bold indicate a temperature range of -40c to +85c. these specific ations are guaranteed by design.
aoz1283 rev. 0.4 june 2012 www.aosmd.com page 5 of 15 block diagram pwm logic enable detect softstart regulator fb en ss 0.8v error amplifier driver comp bst lx fsw vin ramp generator osc pwm comparator gnd current sense bst ldo oc clk
aoz1283 rev. 0.4 june 2012 www.aosmd.com page 6 of 15 typical performance characteristics t a = 25c, v in = 24v, v en = 5v, v out = 5v, unless otherwise specified. out voltage (2v/div) in current (1a/div) lx out voltage (2v/div) inductor current (5a/div) voltage (20v/div) 10ms /div 5ms /div start up to full load short circuit protection full load operation 1s/ div 1s /div in ripple out ripple voltage (1v/div) inductor current (1a/div) lx voltage (20v/div) voltage (1v/div) in ripple out ripple voltage (1v/div) inductor current (2a/div) lx voltage (20v/div) voltage (1v/div) light load operation out voltage (0.5v/div) out current (1a/div) lx out voltage (2v/div) inductor current (5a/div) voltage (20v/div) 10ms /div 100s /div 50% to 100% load transient short circuit recovery
aoz1283 rev. 0.4 june 2012 www.aosmd.com page 7 of 15 efficiency curves 2.5 efficiency (vo=5v, fs=600khz) vs. load current 60 65 70 75 80 85 95 90 1.0 0.5 load current (a) efficiency (%) 2.0 01.5 2.5 efficiency (vo=3.3v, fs=600khz) vs. load current 60 65 70 75 80 85 95 90 100 1.0 0.5 load current (a) efficiency (%) 2.0 01.5 12v?5v 24v?5v 36v?5v 5v?3.3v 24v?3.3v 36v?3.3v 12v?3.3v
aoz1283 rev. 0.4 june 2012 www.aosmd.com page 8 of 15 detailed description the aoz1283 is a current-mode step down regulator with integrated high side nmos switch. it operates from a 3v to 36v input voltage range and supplies up to 4a of load current. features include enable control, power-on reset, input under voltage lockout, external soft-start and thermal shut down. the aoz1283 is availabl e in epad so-8 package. enable and soft start the aoz1283 has external soft start feature to limit in- rush current and ensure the output voltage ramps up smoothly to regulation voltage. a soft start process begins when the input voltage rises to 3v and voltage on en pin is high. in soft start process, a 2.5a internal current source char ges the external capacitor at ss. as the ss capacitor is charged, the voltage at ss rises. the ss voltage clamps the reference voltage of the error amplifier, therefore output voltage rising time follows the ss pin voltage. with the slow ramping up output voltage, the inrush current can be prevented. minimum external soft-start capacitor 850pf is required, and the corresponding soft-start time is about 200s. the en pin of the aoz1283 is active high. connect the en pin to a voltage between 1.2v to 5v if enable function is not used. pull it to grou nd will disable the aoz1283. do not leave it open. the voltage on en pin must be above 1.2v to enable the aoz1283. when voltage on en pin falls below 0.4v, the aoz1283 is disabled. if an application circuit requires the aoz1283 to be disabled, an open drain or open collector circuit should be used to interface to en pin. steady-state operation under steady-state conditions, the converter operates in fixed frequency and continuous-conduction mode (ccm). the aoz1283 integrates an internal n-mosfet as the high-side switch. inductor current is sensed by amplifying the voltage drop across the drain to source of the high side power mosfet. since the n-mosfet requires a gate voltage higher than the input voltage, a boost capacitor connected between lx pin and bst pin drives the gate. the boost capacitor is charged while lx is low. an internal 10 ? switch from lx to gnd is used to insure that lx is pulled to gnd even in the light load. output voltage is divided down by the external voltage divider at the fb pin. the difference of the fb pin voltage and reference is amplified by the internal transconductance error amplifier. the error voltage, which shows on the comp pin, is compared against the current signal, which is sum of inductor current signal and ramp compensation signal, at pwm comparator input. if the current signal is less than the error voltage, the internal high-side switch is on. the inductor current flows from the input through the inductor to the output. when the current signal exceeds the error voltage, the high-side switch is off. the inductor current is freewheeling through the schottky diode to output. switching frequency the AOZ1283PI switching frequency can be programmed by an external resistor. the external resistor value can be calculat ed by the following formula: some standard values of rf for most commonly used switching frequency are listed in table 1. table 1. output voltage programming output voltage can be set by feeding back the output to the fb pin with a resistor divider network. in the application circuit shown in figure 1. the resistor divider network includes r1 and r2. us ually, a design is started by picking a fixed r2 value and calculating the required r1 with equation below. some standard values of r1 and r2 for the most commonly used output voltage values are listed in ta b l e 2 . table 2. fo (hz) rf (k ? ) 200k 249 500k 100 1m 46.6 2m 20 vo (v) r1 (k ? ) r2 (k ? ) 0.8 1.0 open 1.2 4.99 10 1.5 10 11.5 1.8 12.7 10.2 2.5 21.5 10 3.3 31.6 10 5.0 52.3 10 rf k ? ?? 5000 f o khz ?? --------------------- 5 k ? ? = v o 0.8 1 r 1 r 2 ------ - + ?? ?? ?? ? =
aoz1283 rev. 0.4 june 2012 www.aosmd.com page 9 of 15 the combination of r1 and r2 should be large enough to avoid drawing excessive current from the output, which will cause power loss. protection features the AOZ1283PI has multiple protection features to prevent system circuit damage under abnormal conditions. over current protection (ocp) the sensed inductor current si gnal is also used for over current protection. since the aoz1283 employs peak current mode control, the comp pin voltage is proportional to the peak inductor current. the comp pin voltage is limited to be between 0.4v and 2.5v internally. the peak inductor current is automatically limited cycle by cycle. the cycle by cycle current limit threshold is internally set. when the load current reaches the current limit threshold, the cycle by cycle current limit circuit turns off the high side switch immediately to terminate the current duty cycle. the inductor curren t stop rising. the cycle by cycle current limit protection directly limits inductor peak current. the average inductor current is also limited due to the limitation on peak inductor current. when cycle by cycle current limit circuit is triggered, the output voltage drops as the duty cycle decreasing. the aoz1283 has internal short circuit protection to protect itself from catastrophic failure under output short circuit conditions. the fb pin voltage is proportional to the output voltage. whenever fb pin voltage is below 0.2v, the short circuit protection circuit is triggered. power-on reset (por) a power-on reset circuit monito rs the input voltage. when the input voltage exceeds 2.9v, the converter starts operation. when input voltage falls below 2.3v, the converter will st op switching. thermal protection an internal temperature sensor monitors the junction temperature. it shuts down the internal control circuit and high side nmos if the junction temperature exceeds 145oc. the regulato r will restart automat ically under the control of soft-start circuit when the junction temperature decreases to 100oc. application information the basic AOZ1283PI applicat ion circuit is shown in figure 1. component selection is explained as follows. input capacitor the input capacitor (c1 in figure 1) must be connected to the vin pin and gnd pin of the aoz1283 to maintain steady input voltage and filter out the pulsing input current. the voltage rating of input capacitor must be greater than maximum input voltage plus ripple voltage. the input ripple voltage can be approximated by equation below: since the input current is discontinuous in a buck converter, the current stress on the input capacitor is another concern when selecting the capacitor. for a buck circuit, the rms value of input capacitor current can be calculated by: if we let m equal the conversion ratio: the relationship between the input capacitor rms current and voltage conversion ratio is calculated and shown in figure 2. it can be seen that when v o is half of v in , c in is under the worst current stress. the worst current stress on c in is 0.5 x i o . figure 2. i cin vs. voltage conversion ratio ? v in i o fc in ? ----------------- 1 v o v in -------- - ? ?? ?? ?? v o v in -------- - ? ? = i cin_rms i o v o v in -------- - 1 v o v in -------- - ? ?? ?? ?? ? = v o v in -------- - m = 0 0.1 0.2 0.3 0.4 0.5 0 0.5 1 m i cin_rms (m) i o
aoz1283 rev. 0.4 june 2012 www.aosmd.com page 10 of 15 for reliable operation and best performance, the input capacitors must have curr ent rating higher than i cin-rms at worst operating conditions. ceramic capacitors are preferred for input capacitors because of their low esr and high ripple current rating. depending on the application circuits, other low esr tantalum capacitor or aluminum electrolytic capacitor may also be used. when selecting ceramic capacitors, x5r or x7r type dielectric ceramic capacitors are preferred for their better temperature and voltage characteristics. note that the ripple current rating from capacitor manufactures is based on certain amount of life time. further de-rating may be necessary for practical design requirement. inductor the inductor is used to supply constant current to output when it is driven by a switching voltage. for given input and output voltage, inductance and switching frequency together decide the inductor ripple current, which is: the peak inductor current is: high inductance gives low inductor ripple current but requires larger size inductor to avoid saturation. low ripple current reduces inductor core losses. it also reduces rms current through inductor and switches, which results in less conduction loss. when selecting the inductor, make sure it is able to handle the peak current without saturation even at the highest operating temperature. the inductor takes the highest current in a buck circuit. the conduction loss on inductor needs to be checked for thermal and efficiency requirements. surface mount inductors in different shape and styles are available from coilcraft, elytone and murata. shielded inductors are small and radiate less emi noise. but they cost more than unshielded inductors. the choice depends on emi requirement, price and size. output capacitor the output capacitor is selected based on the dc output voltage rating, output ripple voltage specification and ripple current rating. the selected output capacitor must have a higher rated voltage specification than the maximum desired output voltage including ripple. de-rating needs to be considered for long term reliability. output ripple voltage specification is another important factor for selecting the output capacitor. in a buck converter circuit, output ripple voltage is determined by inductor value, switching frequency, output capacitor value and esr. it can be calculated by the equation below: where, c o is output capacitor value, and esr co is the equivalent series resistance of the output capacitor. when low esr ceramic capacitor is used as output capacitor, the impedance of the capacitor at the switching frequency dominates. output ripple is mainly caused by capacitor value and inductor ripple current. the output ripple voltage calculation can be simplified to: if the impedance of esr at switching frequency dominates, the output ripple voltage is mainly decided by capacitor esr and inductor ripple current. the output ripple voltage calculation can be further simplified to: for lower output ripple voltage across the entire operating temperature range, x5r or x7r dielectric type of ceramic, or other low esr tantalum capacitor or aluminum electrolytic capa citor may also be used as output capacitors. in a buck converter, output capacitor current is continuous. the rms current of output capacitor is decided by the peak to peak inductor ripple current. it can be calculated by: usually, the ripple current rating of the output capacitor is a smaller issue because of the low current stress. when the buck inductor is selected to be very small and inductor ripple current is high, output capacitor could be overstressed. ? i l v o fl ? ---------- - 1 v o v in -------- - ? ?? ?? ?? ? = i lpeak i o ? i l 2 -------- + = ? v o ? i l esr co 1 8 fc o ? ? ------------------------- + ?? ?? ? = ? v o ? i l 1 8 fc o ? ? ------------------------- ?? ?? ? = ? v o ? i l esr co ? = i co_rms ? i l 12 ---------- =
aoz1283 rev. 0.4 june 2012 www.aosmd.com page 11 of 15 schottky diode selection the external freewheeling diode supplies the current to the inductor when the high side nmos switch is off. to reduce the losses due to the forward voltage drop and recovery of diode, schottky diode is recommended to use. the maximum reverse voltage rating of the chosen schottky diode should be greater than the maximum input voltage, and the current rating should be greater than the maximum load current. low input operation when v in is lower than 4.5v, such as 3.0v, an external 5v is required to add into the bst pin for proper operation. loop compensation the aoz1283 employs peak current mode control for easy use and fast transient response. peak current mode control eliminates the double pole effect of the output l&c filter. it greatly simp lifies the compensation loop design. with peak current mode control, the buck power stage can be simplified to be a one-pole and one-zero system in frequency domain. the pole is dominant pole and can be calculated by: the zero is a esr zero due to output capacitor and its esr. it is can be calculated by: where; c o is the output filter capacitor; r l is load resistor value and esr co is the equivalent series resistance of output capacitor. the compensation design is actually to shape the converter close loop transfer function to get desired gain and phase. several different types of compensation network can be used for ao z1283. for most cases, a series capacitor and resistor network connected to the comp pin sets the pole-zero and is adequate for a stable high-bandwidth control loop. in the aoz1283, fb pin and comp pin are the inverting input and the output of internal transconductance error amplifier. a series r and c compensation network connected to comp provides one pole and one zero. the pole is: where; g ea is the error amplifier transconductance, which is 20010 -6 a/v; g vea is the error amplifier voltage gain, which is 500 v/v and c c is compensation capacitor. the zero given by the exter nal compensation network, capacitor c c (c 5 in figure 1) and resistor r c (r 1 in figure 1), is located at: to design the compensation circuit, a target crossover frequency f c for close loop must be selected. the system crossover frequency is where control loop has unity gain. the crossover frequency is also called the converter bandwidth. generally a higher bandwidth means faster response to load transient. however, the bandwidth should not be too high due to system stability concern. when designing the compensation loop, converter stability under all line and load condition must be considered. usually, it is recommended to set the bandwidth to be less than 1/10 of switching frequency. the strategy for choosing r c and c c is to set the cross over frequency with r c and set the compensator zero with c c . using selected cr ossover frequency, f c , to calculate r c : where; f c is desired crossover frequency; v fb is 0.8v; g ea is the error amplifier transconductance, which is 20010 -6 a/v and g cs is the current sense circuit transconductance, which is 4.5 a/v. l o p r c f ? ? ? ? 2 1 1 co o z esr c f ? ? ? ? 2 1 1 vea c ea p g c g f ? ? ? ? 2 2 c c z r c f ? ? ? ? 2 1 2 cs ea o fb o c c g g c v v f r ? ? ? ? ? ? 2
aoz1283 rev. 0.4 june 2012 www.aosmd.com page 12 of 15 the compensation capacitor c c and resistor r c together make a zero. this zero is put somewhere close to the dominate pole f p1 but lower than 1/5 of selected crossover frequency. c c can is selected by: equation above can also be simplified to: easy to use application software which helps to design and simulate the compensation loop can be found at www.aosmd.com . thermal management and layout consideration in the aoz1283 buck regulator circuit, high pulsing current flows through two circuit loops. the first loop starts from the input capacitors, to the vin pin, to the lx pins, to the filter inductor, to the output capacitor and load, and then return to the input capacitor through ground. current flows in the first loop when the high side switch is on. the second loop starts from inductor, to the output capacitors and load, to the gnd pin of the aoz1283, to the lx pins of the aoz1283. current flows in the second loop when the low side diode is on. in pcb layout, minimizing the two loops area reduces the noise of this circuit and im proves efficiency. a ground plane is recommended to connect input capacitor, output capacitor, and gnd pin of the aoz1283. in the aoz1283 buck regulator circuit, the three major power dissipating components are the aoz1283, external diode and output inductor. the total power dissipation of converter circ uit can be measured by input power minus output power. the power dissipation of inductor can be approximately calculated by output curr ent and dcr of inductor: the power dissipation of diode is: the actual junction temperature can be calculated with power dissipation in the aoz1283 and thermal impedance from junction to ambient. the maximum junction temperature of AOZ1283PI is 145oc, which limits the maximum load current capability. the thermal performance of the aoz1283 is strongly affected by the pcb layout. extra care should be taken by users during design process to ensure that the ic will operate under the recommended environmental conditions. several layout tips are listed below for the best electric and thermal performance. 1. do not use thermal relief connection to the vin and the gnd pin. pour a maximized copper area to the gnd pin and the vin pin to help thermal dissipation. 2. input capacitor should be connected to the vin pin and the gnd pin as close as possible. 3. make the current trace from lx pins to l to co to the gnd as short as possible. 4. pour copper plane on all unused board area and connect it to stable dc nodes, like vin, gnd or vout. 5. keep sensitive signal trace such as trace connected with fb pin and comp pin far away from the lx pins. 1 2 5 . 1 p c c f r c ? ? ? ? c l o c r r c c ? ? p total_loss v in i in ? ?? v o v in ? ?? ? = p inductor_loss i o 2 r inductor 1.1 ? ? = p diodeloss i o f v ? 1 v o v in -------- - ? ?? ?? ?? ? = t junction p total_loss p diode_loss ? p inductor_loss ? ?? ? ja t + ambient -------------------------------------------------------------------------------------------------------------------------- =
aoz1283 rev. 0.4 june 2012 www.aosmd.com page 13 of 15 package dimensions, so-8 ep1 notes: 1. package body sizes exclude mold flash and gate burrs. 2. dimension l is measured in gauge plane. 3. tolerance 0.10mm unless otherwise specified. 4. controlling dimension is millimeter, converted inch dimensions are not necessarily exact. 5. die pad exposure size is according to lead frame design. 6. followed from jedec ms-012 symbols a a1 a2 b c d d0 d1 e e e1 e2 e3 l y | l1?l1' | l1 dimensions in millimeters recommended land pattern min. 1.40 0.00 1.40 0.31 0.17 4.80 3.20 3.10 5.80 ? 3.80 2.21 0.40 ? 0 ? d0 unit: mm nom. 1.55 0.05 1.50 0.406 ? 4.96 3.40 3.30 6.00 1.27 3.90 2.41 0.40 ref 0.95 ? 3 0.04 1.04 ref max. 1.70 0.10 1.60 0.51 0.25 5.00 3.60 3.50 6.20 ? 4.00 2.61 1.27 0.10 8 0.12 dimensions in inches d1 e1 e e3 e2 note 5 l1' l1 l gauge plane 0.2500 c d 7 (4x) b 3.70 2.20 2.87 2.71 5.74 1.27 0.80 0.635 e a1 a2 a symbols a a1 a2 b c d d0 d1 e e e1 e2 e3 l y | l1?l1' | l1 min. 0.055 0.000 0.055 0.012 0.007 0.189 0.126 0.122 0.228 ? 0.150 0.087 0.016 ? 0 ? nom. 0.061 0.002 0.059 0.016 ? 0.195 0.134 0.130 0.236 0.050 0.153 0.095 0.016 ref 0.037 ? 3 0.002 0.041 ref max. 0.067 0.004 0.063 0.020 0.010 0.197 0.142 0.138 0.244 ? 0.157 0.103 0.050 0.004 8 0.005
aoz1283 rev. 0.4 june 2012 www.aosmd.com page 14 of 15 carrier tape reel tape size 12mm reel size ?330 m ?330.00 0.50 package so-8 (12mm) a0 6.40 0.10 b0 5.20 0.10 k0 2.10 0.10 d0 1.60 0.10 d1 1.50 0.10 e 12.00 0.10 e1 1.75 0.10 e2 5.50 0.10 p0 8.00 0.10 p1 4.00 0.10 p2 2.00 0.10 t 0.25 0.10 n ?97.00 0.10 k0 unit: mm b0 g m w1 s k h n w v r trailer tape 300mm min. or 75 empty pockets components tape orientation in pocket leader tape 500mm min. or 125 empty pockets a0 p1 p2 feeding direction p0 e2 e1 e d0 t d1 w 13.00 0.30 w1 17.40 1.00 h ?13.00 +0.50/-0.20 k 10.60 s 2.00 0.50 g ? r ? v ? leader/trailer and orientation unit: mm tape and reel dimensions, so-8 ep1
aoz1283 rev. 0.4 june 2012 www.aosmd.com page 15 of 15 part marking z1283pi fay part number code assembly lot code year & week code wlt fab & assembly location AOZ1283PI (so-8) as used herein: 1. life support devices or systems are devices or systems which, (a) are intended for surgical implant into the body or (b) support or sustain life, and (c) whose failure to perform when properly used in accordance with instructions for use provided in the labeling, can be reasonably expected to result in a significant injury of the user. 2. a critical component in any component of a life support, device, or system whose failure to perform can be reasonably expected to cause the failure of the life support device or system, or to affect its safety or effectiveness. this data sheet contains preliminary data; supplementary data may be published at a later date. alpha & omega semiconductor reserves the right to make changes at any time without notice. life support policy alpha & omega semiconductor products are not authorized for use as critical components in life support devices or systems.

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